Radio frequency circuit

ABSTRACT

A digital-to-analog conversion circuit operates by selectively discharging members of a plurality of capacitors. Charging of the capacitors occurs during a reset period while digital-to-analog conversion occurs as the capacitors are discharged. Those capacitors that are discharged are selected from the plurality of capacitors based on a digital input. The analog output includes the charge discharged from the capacitors. The capacitors are optionally divided into separate capacitor banks.

CROSS-REFERENCE TO PRIORITY APPLICATION

The present U.S. Utility patent application claims priority pursuant to35 U.S.C. §121, as a divisional, to the following U.S. Utility patentapplication which is hereby incorporated herein by reference in itsentirety and made part of the present U.S. Utility patent applicationfor all purposes:

1. U.S. Utility application Ser. No. 12/564,810 entitled “RadioFrequency Circuit,” (Attorney Docket No. BP23186) filed Sep. 22, 2009,pending.

BACKGROUND

1. Field of the Invention

The invention is in the field of electronics and more specifically inthe field of digital-to-analog converters.

2. Related Art

There are a variety of digital-to-analog converters. In one type ofdigital-to-analog converter a single capacitor is charged using aplurality of digitally switched current inputs. Each of the currentinputs is configured to supply a share of a charging current. The amountof charging is dependent on the current or voltage sources, on thesettings of the switches and, thus, the digital values used to controlthe switches. Charging is continued for a fixed time or until athreshold voltage is reached. For example, if the charging is continuedfor a fixed time then the resulting charge on the capacitor is used toproduce an analog voltage or current.

The accuracy of this type of digital-to-analog converter is, in part,dependant on the accuracy of the current or voltage sources and/ortiming elements. The precision of this type of digital-to-analogconverter is dependant, in part, on the number of current input switchesand/or the length of the measured time period.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates a digital-to-analog circuit, according to variousembodiments of the invention.

FIGS. 2A and 2B illustrate waveforms, according to various embodimentsof the invention.

FIGS. 3A-3C illustrate digital-to-analog circuit elements including adifferential output, according to various embodiments of the invention.

FIG. 4 illustrates an alternative digital-to-analog circuit element,according to various embodiments of the invention.

FIG. 5 illustrates a digital-to-analog circuit including more than onemultiple capacitor bank, according to various embodiments of theinvention.

FIGS. 6A-6C illustrates output waveforms generated using two capacitorbanks, according to various embodiments of the invention.

FIG. 7 illustrates a digital-to-analog circuit including boththermometer and a binary bank, according to various embodiments of theinvention.

FIG. 8 illustrates a transmitter system, according to variousembodiments of the invention.

FIG. 9 illustrates a method of converting a digital input signal to ananalog output signal, according to various embodiments of the invention.

FIG. 10 illustrates a digital-to-analog circuit in which capacitors arecharged based on a digital input, according to various embodiments ofthe invention.

FIGS. 11A-11C illustrates alternative output circuits, according tovarious embodiments of the invention.

FIGS. 12A-12C include a timing diagram of a digital-to-analog circuitincluding a summing capacitor, according to various embodiments of theinvention.

FIG. 13 illustrates methods of converting a digital input signal to ananalog output signal, according to various embodiments of the invention.

FIG. 14 illustrates an I/Q Modulation System 1400 in configured tosuppress one of two sidebands.

FIGS. 15A and 15B illustrate two alternative circuits in which adigital-to-analog circuit is used to both perform a digital-to-analogconversion and also achieve sideband suppression.

FIG. 16 illustrates an alternative digital-to-analog circuit element,according to various embodiments of the invention.

FIG. 17 illustrates an example of a bootstrapped switch, according tovarious embodiments of the invention.

SUMMARY

The invention includes a digital-to-analog converter in which thedischarge of a plurality of capacitors is used to produce an analogcharge output. Either the charging or discharging of the plurality ofcapacitors is digitally controlled. For example, in various embodiments,each of these capacitors is first charged to one or more predeterminedvoltages. After charging, the charging source is electrically decoupledfrom the plurality of capacitors. Switches are then set responsive to adigital input to discharge a selected subset of the plurality ofcapacitors. The identities of the capacitors included in the subset ofthe plurality of capacitors are dependent on the digital input. Theanalog power (e.g., charge and current) of the discharge is, thus, afunction of the digital input. Alternatively, switches are used tocharge only a subset of the plurality of capacitor responsive to thedigital input. The charged capacitors are discharged and the analogpower of the discharge is, thus, a function of the digital input.

The output of the digital-to-analog converter is optionally coupled to alow impedance load such as a power amplifier, transformer, currentcopier, antenna, or the like. This load may be part of a communicationmedium, e.g., a wire or wireless medium. The digital-to-analog converterof the invention is optionally configured to operate at radiofrequencies.

In some embodiments, the digital-to-analog converter includes a summingcapacitor configured to collect the charge from the subset ofselectively charged or discharged capacitors and then provide thecollected charge as the analog output of the digital-to-analogconverter. Use of the summing capacitor provides for an RC time constantof the analog output that is independent of the digital input.

Various embodiments if the invention include a digital-to-analogconverter comprising: a plurality of capacitors; one or more voltagesources configured for recharging the plurality of capacitors; aplurality of recharge switches disposed between the one or more voltagesources and the plurality of capacitors, each of the plurality ofrecharge switches being configured to control recharging of one of theplurality of capacitors, respectively; a plurality of discharge switcheseach respectively configured to discharge one of the plurality ofcapacitors to produce a differential analog output; and a controlcircuit configured to select which of the plurality of capacitors tocharge and discharge using one or more of the plurality of dischargeswitches or one or more of the plurality of recharge switches, theselection being based on the value of a digital input and the analogoutput including a pulse of charge representative of the digital input.

Various embodiments of the invention include a digital-to-analogconverter comprising: a first capacitor; a second capacitor; one or morevoltage sources configured to charge the first capacitor and the secondcapacitor; a first recharge switch disposed between the first capacitorand the one or more voltage sources; a second recharge switch disposedbetween the second capacitor and the one or more voltage sources; afirst discharge switch configured to discharge the first capacitor; asecond discharge switch configured to discharge the second capacitor;and an output circuit configured to receive the discharge of the firstcapacitor through the first discharge switch, to receive the dischargeof the second capacitor through the second discharge switch, and toprovide a combination of charge discharged from the first capacitor andcharge discharged from the second capacitor as a differential analogoutput pulse of the digital-to-analog converter.

Various embodiments of the invention include a radio frequencytransmitter comprising: a data latch configured to receive a digitaldata signal in a first frequency band; a digital-to-analog converterconfigured to receive the digital data signal from the data latch and togenerate a differential output signal modulated to form a secondfrequency of at least 0.8 GHz, the output signal comprising a series ofpulses including charge representative of the digital data; a bandselection filter configured to receive the output signal of thedigital-to-analog converter; an amplifier configured to amplify theoutput signal of the digital-to-analog converter; and a couplerconfigured to receive the output signal of the digital-to-analogconverter and to couple this output signal to a communication medium atthe second frequency.

Various embodiments of the invention include a method of converting adigital input signal to an analog output signal, the method comprising:receiving the digital signal including at least two bits; charging botha first capacitor and a second capacitor at the same time using one ormore voltage sources; opening a first recharge switch to electricallydisconnect the first capacitor from the one or more voltage sources;opening a second recharge switch to electrically disconnect the firstcapacitor from the one or more voltage sources; setting a firstdischarge switch configured to control discharge of the first capacitor;setting a second discharge switch configured to control discharge of thesecond capacitor, wherein charging of the first and second capacitor orsetting of the first and second discharge switches is responsive to thetwo bits; and providing a charge pulse through the first dischargeswitch and the second discharge switch, the analog output beingdifferential and including charge discharged from the first capacitorand the second capacitor.

Various embodiments of the invention include a sideband suppressionsystem comprising: a clock configured to provide a clock signal; an I/Qdata latch configured to receive digital input data and provide an “I”signal and a “Q” signal representative of the digital input data; aphase shifter configured to produce a phase shifted copy of the clocksignal; a first differential digital-to-analog converter configured toreceive the “I” signal and the clock signal, and to produce a firstanalog output including two sidebands of the “I” signal around asampling frequency of the first digital-to-analog converter; a seconddifferential digital-to-analog converter configured to receive the “Q”signal and the phase shifted copy of the clock signal, and to produce asecond analog output including two sidebands of the “Q” signal around asampling frequency of the second digital-to-analog converter; and a loadcircuit configured to combine the first and second analog outputs so asto produce a single sideband output.

Various embodiments of the invention include a sideband suppressionsystem comprising: a clock configured to provide a clock signal; an I/Qdata latch configured to receive digital input data and provide an “I”signal and a “Q” signal; a multiplexer configured to multiplex the “I”and “Q” signals; a binary negator configured to negate an output of themultiplexer output on every other cycle of the clock signal; adifferential digital-to-analog converter configured to receive an outputof the binary negator and produce an analog charge pulse outputrepresentative of the digital input data, the analog charge pulse outputincluding a single sideband of the clock signal, a second sideband beingsuppressed; and a load circuit configured to receive the analog chargepulse output.

DETAILED DESCRIPTION

In contrast with some systems of the prior art, wherein charging of acapacitor is used to convert a digital input to an analog output,various embodiments of the invention comprise selective discharging of aplurality of capacitors to generate an analog output. This approachprovides a number of advantages. As is further shown elsewhere herein,the approach of selectively discharging different capacitors can beimplemented using a variety of alternative circuits. Because the systemcan be configured such that the time required to perform the dischargeprocess is shorter than the time required to charge the capacitors, thefrequency of the digital-to-analog conversion can be less dependent onthe RC time constant of the charging process relative to systems of theprior art. In various embodiments, the digital-to-analog circuit of theinvention is implemented in CMOS technology and/or is configured toprovide an analog output at a frequency of at least 1, 1.5, 2, 2.2, 5,10 or 50 GHz. The frequency of the output signal can be 2, 5, 10, 50 or100 times greater than a frequency or frequency band at which thedigital input is received. For example, in one embodiment data isreceived at approximately 200 MHz while the output frequency isapproximately 2.2 GHz. In other embodiments, the output frequency isabove 800 MHz, above 1.5 GHz, above 2.0 GHz, or between approximately2.0 and 2.2 GHz. In some embodiments, the output frequency is one ormore frequency range typically used for prior art digital broadcast suchas cable television, satellite television, wireless communication, orthe like. The output frequency may be in the ranges 800 MHz-1200 MHz,1500 MHz-2 GHz, or 2.2 GHz-2.8 GHz. The output frequency optionallyincludes a frequency band at least 50 Mhz, 100 Mhz, 200 MHz or 250 MHzin width. The output may include one or two sidebands of a samplingfrequency of the digital to analog converter. (The output frequencydiscussed herein is the frequency at which output pulses are generated,e.g., one over the period between pulses, and not frequency componentsthat may be found within the pulses.) The sampling frequency of thedigital-to-analog converter is optionally between 700 MHz and 3.2 GHzdepending on the digital baseband and technique used for generating asideband.

FIG. 1 illustrates a Digital-to-Analog Circuit 100, according to variousembodiments of the invention. Digital-to-Analog Circuit 100 isconfigured to receive an n bit digital signal at a Digital Input Circuit105 and to generate a responsive analog signal at an Output Circuit 110.Digital-to-Analog Circuit 100 includes a plurality of Unit Cells 115each comprising at least one Capacitor 120, individually labeled 120A,120B, etc. Each Unit Cell 115 further comprises a Recharge Switch 125and a Discharge Switch 130, individually labeled 125A, 125B . . . and130A, 130B . . . , respectively. Recharge Switches 125 are controlled bya Control Circuit 135, while switches 130 are controlled by DigitalInput Circuit 105 and Control Circuit 135. One side of each ofCapacitors 120 is coupled to respective members of Recharge Switches 125and 130 while the other side is typically coupled to a fixed voltagesuch as ground or common. Recharge Switches 125 are disposed between oneor more Voltage Sources 140 and Capacitors 120 are each configured tocontrol recharging of one of the plurality of Capacitors 120. DischargeSwitches 130 are disposed between Capacitors 120 and Output Circuit 110and are each configured to control discharging of one of Capacitors 120by selectively opening and closing responsive to a digital input.Digital Input Circuit 105 is optionally considered part of ControlCircuit 135.

Voltage Source 140 is configured to charge Capacitors 120 when RechargeSwitches 125 are in a closed position. Voltage Source 140 may include asingle device, e.g. a high current power supply, configured to providecurrent to several or all of Recharge Switches 125. Alternatively,Voltage Source 140 may include several devices each connected to providecurrent to a different member of Recharge Switches 125. In someembodiments, Voltage Source 140, Recharge Switches 125 and Capacitors120 are configured to minimize the RC time constant associated withcharging Capacitors 120 while Recharge Switches 125 are in a closedstate.

Recharge Switches 125 and Discharge Switches 130 are typically solidstate switches, e.g., transistors. However, in alternative embodimentsRecharge Switches 125 and/or Discharge Switches 130 include electricallyor magnetically actuated mechanical devices. In some embodiments,Recharge Switches 125 and Discharge Switches 130 are included in amulti-pole switch. In these embodiments, a first pole position isconfigured to electrically couple one of Capacitors 120 to VoltageSource 140 and a second pole position is configured to electricallycouple the same Capacitor 120 to Output Circuit 110.

Control Circuit 135 is configured to electrically control the state ofRecharge Switches 125A-125D and thereby control the charging ofCapacitors 120. Control Circuit 135 is also configured to control thestate of Discharge Switches 130 via Digital Input Circuit 105. Forexample, Control Circuit 135 is configured to close Recharge Switches125 during a recharge period and to close members Discharge Switches 130during a conversion period. During the recharge period DischargeSwitches 130 are in the open state and during the conversion periodRecharge Switches 120 are typically in the open state. Control Circuit135 typically includes a timing circuit configured to time the changesbetween the recharge periods and the conversion period.

During the conversion period Digital Input Circuit 105 is configured todetermine which members of Discharge Switches 130 are placed in theclosed (conducting) state and which are placed in the open state. Thoseswitches in the closed state allow charge on the member of Capacitors120 within the same Unit Cell 115 to be discharged to Output Circuit110. In some embodiments, Digital input Circuit 105 includes a set ofvoltage followers each configured to receive one bit of the digitalinput signal to be converted to an analog signal. These voltagefollowers drive the changes in the inputs of Discharge Switches 130 thatcontrol the switch states. One or more signals from Control Circuit 135are used to determine at what times the digital input signal is used toset the states of Discharge Switches 130.

Output Circuit 110 is configured to receive the discharge of a set ofCapacitors 120 and to provide a resulting output. Which members ofCapacitors 120 are included in this set is responsive to the states ofDischarge Switches 130 and, thus, responsive to the digital input toDigital Input Circuit 105. Output Circuit 110 typically receivesdischarge from several of Capacitors 120 at the same time, e.g., in aconversion period. These discharges are combined and used to provide anoutput. For example, in one instance Output Circuit 100 may receive adischarge from Capacitor 120A via Discharge Switch 130A, at the sametime receive a discharge from Capacitor 120B via Discharge Switch 130B,and combine these discharges. The output may be treated as a current ora voltage. For example, in some embodiments, Output Circuit 110 includesa current follower configured to minor a current received as part of thecombined discharge. In some embodiments, Output Circuit 110 includes animpedance (e.g., resistor) configured to cause a voltage differentialwhen the combined discharge is passed through the impedance. In variousembodiments, Output Circuit 110 includes an antenna, a balun, a wiredcommunication channel, and or the like. In various embodiments, OutputCircuit 110 is configured to couple the output into a high frequencycommunication system such as coax cable, a wireless device, or the likeOutput Circuit 110 is typically configured to appear as a low impedancecurrant sink from the point of view of Capacitors 120. Variousalternative embodiments of Output Circuit 110 are discussed elsewhereherein.

The Digital-to-Analog Circuit 100 is typically configured to operate asfollows. During the recharge period Control Circuit 135 closes RechargeSwitches 125. The closure of Recharge Switches 125 allows current fromVoltage Source 140 to recharge Capacitors 120. Capacitors 120 areoptionally fully charged during the recharge period. At the end of therecharge period Recharge Switches are opened to isolate Capacitors 120from Voltage Source 140. In the conversion period, which follows therecharge period, some or all of Discharge Switches 130 are closed byControl Circuit 135 and Digital Input Circuit 105. Control Circuit 135is configured to control the timing of this switch closing while DigitalInput Circuit 105 is configured to control which of Discharge Switches130 are closed and which are left open. By closing some of all ofDischarge Switches 130 charge is allowed to flow from Capacitors 120 toOutput Circuit 110. This charge represents the analog output ofDigital-to-Analog Circuit 100 and may be used as a voltage or currentwithin Output Circuit 110. Further details of this operation arediscussed elsewhere herein.

While the embodiments illustrated in FIG. 1 include four Unit Cells 115,alternative embodiments may include 2, 3 or more Unit Cells 115. Forexample, some embodiments in a thermometer configuration include n unitcells where n is the number of bits of digital data received by DigitalInput Circuit 150 to be converted to an analog signal. Some embodiments,in a binary configuration, include 2^(n)−1 unit cells where n is thenumber of bits of digital data received by Digital Input Circuit 150 tobe converted to an analog signal. As is further described herein, theUnit Cells 115 included in Digital-to-Analog Circuit 100 may include avariety of types and or configurations.

FIGS. 2A and 2B illustrate waveforms over several recharge andconversion periods, according to various embodiments of the invention.In FIG. 2A the total output power, as may be found at output Circuit110, is illustrated as a function of time. In FIG. 2B the charge on oneof Capacitors 120 is illustrated over the same time scale. During aConversion Period 210 Capacitors 120 are discharged through DischargeSwitches 130 to provide power at Output Circuit 110. The length of thisdischarge is a function of the RC time constant of Capacitors 120, theimpedance of Discharge Switches 130 and the impedance into OutputCircuit 110. The total power of the discharge is dependent on whichmembers of Capacitors 120 are discharged, which is dependent on thedigital input value received at Digital Input Circuit 105. For example,in FIG. 2A one of the output pulses is of lower magnitude than the otherthree. This difference in magnitude reflects a change in the members ofCapacitors 120 that are discharged in each Conversion Period 210. Thischange is illustrated by FIG. 2B in which one of Capacitors 120 is notdischarged during the third Conversion Period 210. Recharge Switches 125are in an open state during Conversion Period 210.

Recharge Period 220 is followed by a Recharge Period 220. DuringRecharge Period 220 Capacitors 120 are recharged through RechargeSwitches 125, and all of Discharge Switches 130 are in an open state.The length of Recharge Period 220 is dependent on the RC time constantof Capacitors 120 and the output impedance of Voltage Source 140.Recharge Period 220 may be longer than or shorter than Conversion Period210. An optional Gap 230, during which neither recharging nordischarging occurs, may occur before or after Recharge Period 220.

Through repeated recharge and conversion periods, the output comprises aseries Pulses 235 whose area and height are representative of thedigital input. The Period 240 between the Pulses 235 is dependent on thefrequency at which the recharge and conversion periods occur and theminimum Period 240 is dependent on the length of the recharge andconversion periods. The frequency of the output, e.g., the samplingfrequency, is one over the Period 240. In some embodiments, the outputis viewed as a mixing of the digital input signal with the samplingfrequency. This mixing may be used to move the digital input signal upto a higher frequency domain. Because this mixing is a result of thedigital-to-analog conversion process, an additional mixer is notrequired to move the signal to higher frequencies. The output ofDigital-to-Analog Circuit 100 is in the form of a pulse of chargeresulting from the discharge of capacitors. The charge is representativeof the digital input. Although this charge may be converted to a voltageor a current, providing an output in the form of a delivery of charge isin contrast with digital-to-analog systems of the prior art, whichtypically provide a current or voltage that is representative of adigital input.

FIGS. 3A-3C illustrate digital-to-analog circuit elements including aDifferential Output 310, according to various embodiments of theinvention. The circuit elements illustrated represent embodiments ofUnit Cell 115. These embodiments of Unit Cell 115 may be included withinDigital-to-Analog Circuit 100, optionally in combination with differentembodiments of Unit Cell 115. The Differential Output 310 is optionallyelectrically coupled to a differential embodiment of Output Circuit 110.In FIG. 3A-3C “+” and “−” symbols are used to indicate differentvoltages, which may or may not be of different sign. A differentialoutput is an output in the form of a relative difference between twopoints. This difference can be voltage, current, charge, power, etc, andis typically a function of an input. A differential output is sometimespreferable in that it can reduce certain types of noise. As used herein,a circuit is considered differential if it has a differential output ora single ended output that is generated from an intermediatedifferential circuit. For example, in some embodiments, DifferentialOutput 310 includes an active or passive Balun configured to receive adifferential signal from one or more Unit Cells 115 and to produce asingle ended output. In these embodiments, Digital-to-Analog Circuit 100is still considered differential because of the intermediatedifferential signals received from the one or more Unit Cells 115.

The circuit of FIG. 3A includes Charging Input 315A and optionallyCharging Input 315B configured to receive charging currents of differentmagnitude and/or different sign. For example, in one embodiment theCharging Input 315A is coupled to an output of Voltage Source 140configured to charge Capacitors 120 to +5V, while the Charging Input315B is coupled to an output of Voltage Source 140 configured to chargeCapacitors 120 to −5V. In another embodiment Charging Input 315B iscoupled to an output of Voltage Source 140 configured to chargeCapacitors 120 to +0.5V. In typical operation the two different ChargingInputs 315A and 315B are used in alternating charging periods. In afirst Recharge Period 220 Recharge Switch 125E is closed, while optionalRecharge Switch 125F is opened, thus charging Capacitor 120 to a firstvoltage. In the next Recharge Period 220 Recharge Switch 125F is closed,while Recharge Switch 125E is open, thus charging Capacitor 120 to asecond voltage. The result of this operation is a differential poweroutput at Output Circuit 110 in which different analog outputs appear inalternative cycles. Discharge Switches 130E and optionally 130F areconfigured to control to which side of Differential Output 310 aparticular discharge is delivered. In some embodiments, when RechargeSwitch 125F is used to charge Capacitor 120 Discharge Switch 130F isused to discharge, and when Recharge Switch 125E is used to chargeCapacitor 120 Discharge Switch 130E is used to discharge. The differentanalog outputs are optionally treated as a single differential output.In other modes of operation Recharge Switch 125F is optional and one ofDischarge Switches 130E and 130F are closed responsive to a digitalinput.

The circuit of FIG. 3B provides a differential output whose polarity canbe controlled by selective setting of Recharge Switches 125E-125H.Capacitor 120A can be charged from Charging Input 315A by closingRecharge Switch 125E, or alternatively charged from Charging Input 315Bby closing Recharge Switch 125F. If Charging Inputs 315A and 315B arecoupled to different voltage level outputs of Voltage Source 140, thenthe voltage to which Capacitor 120 A is charged can be controlled byselecting which of Recharge Switches 125E or 125F to close. Likewise,Capacitor 120B can be charged from Charging Input 315A by closingRecharge Switch 125G, or alternatively charged from Charging Input 315Bby closing Recharge Switch 125H In typical operation Charging Switches125E and 125H are closed together, and Charging Switches 125F and 126Gare closed together. The polarity of Differential Output 310 isdetermined by which pair of charging switches are closed together, whichin turn is determined by a digital input bit. The circuit of FIG. 3B maybe treated as one or two Unit Cell 115. In alternative embodiments asingle Unit Cell 115 is coupled to more than two charging voltages andincludes Charging Inputs 315 and Recharge Switches 125 configured toselectively charge a capacitor to more than two alternative voltages.Both Discharge Switches 130E and 130F are typically both closed duringdischarge.

The circuit of FIG. 3C is functionally similar to that of FIG. 3B.However, a single Capacitor 120 is allowed to float between the voltageapplied to Charging Input 315A and Charging Input 315B. The charge oneach side of Capacitor 120 is provided to Differential Output 315 whenDischarge Switches 130E and 130F are closed together during ConversionPeriod 210. The circuit of FIG. 3C represents one Unit Cell 115.

FIG. 4 illustrates alternative embodiments of Unit Cell 115, accordingto various embodiments of the invention. These embodiments includecharging a capacitor and then using a transistor to control providingthe charge as an output. A voltage from Charging Input 315A is passedthrough Charging Switch 125A to Charge Capacitor 120A. In FIG. 4 a solidstate example of Charging Switch 125A is illustrated. This example ofCharging Switch 125A includes a pair of Transistors 410 and 420. Thebases of Transistors 410 and 420 receive voltages at Inputs 430 and 440,respectively. In typical operation Input 430 will receive a voltagerepresentative of a logical 1 or 0, while Input 440 will receive avoltage representative of the logical NOT of the input represented atInput 430. For example, when Input 430 receives a voltage representing alogical 1 Input 440 will receive a voltage representative of a logical0. The voltages at Inputs 430 and 440 will control whether current canflow from Charging Input 315A to charge Capacitor 120.

A Transistor 450 is used in place of Discharge Switch 130A. Transistor450 will prevent discharge of Capacitor 120A as long as the voltage atthe source of Transistor 450 (to which Capacitor 120A is connected) isless than or equal to a voltage at a Gate Input 460 of Transistor 450.In typically operation the voltage at Gate Input 460 is the same as thatat Charging Input 315A. Thus, the charging of Capacitor 120A fromCharging Input 315A through Switch 125A is not sufficient to turn onTransistor 450.

One side of Capacitor 120A is coupled to a Discharge Trigger Input 470.Application of a trigger voltage to this side of Capacitor 120A can beused to increase the voltage on the side of Capacitor 120A to whichTransistor 450 is coupled. Specifically, application of an appropriatetrigger voltage to Discharge Trigger Input 470 can be used to raise thevoltage at the source of Transistor 450 to a voltage that is greaterthan the voltage at Gate Input 460 (plus a junction potential). Thisturns on, e.g., reduces the source-drain impedance of Transistor 450 andallows the discharge of Capacitor 120A through Transistor 450 to OutputCircuit 110. The approach to Unit Cell 115 illustrated in FIG. 4 can bereferred to as the “charge and spill” approach.

Alternative embodiments of Unit Cell 115 will be apparent to one ofordinary skill in the art. Different types of Unit Cell 115 may be usedin the same Digital-to-Analog Circuit. As is discussed further herein,Unit Cells 115 may be separated into different banks or modules.

FIG. 5 illustrates a digital-to-analog circuit including more than onebank of Unit Cells 115, according to various embodiments of theinvention. A First Bank 510 and a Second Bank 515 are illustrated,however alternative embodiments include more than two banks. The outputsof First Bank 510 and Second Bank 515 are combined at Output Circuit 110to produce a single output signal. First Bank 510 and Second Bank 515may be operated in parallel or serially. In parallel operation theConversion Period 210 of each bank occurs at essentially the same time.The use of more than one bank allows for a greater amount of outputpower and/or the conversion of a greater number of decimal bits. Inserial operation the Conversion Period 210 of First Bank 510 occurs at adifferent time than the Conversion Period 210 of Second Bank 515. Inrepetitive cycles digital-to-analog conversion may alternate betweenFirst Bank 510 and Second Bank 515. This allows conversion to occur in ashorter period than the sum of a single Conversion Period 210 andRecharge Period 220, and allows the output of Output Circuit 110 to beat a greater frequency than would be possible using First Bank 510 orSecond Bank 515 alone.

In some embodiments Control Circuit 135 is controllable to operate FirstBank 510 and Second Bank 515 in either a parallel or serial mode. In theparallel mode each of Recharge Switches 125, in both First Bank 510 andSecond Bank 515 are opened and closed at approximately the same timeLikewise, selected members of Discharge Switches 130 in both banks areopened and closed at approximately the same time. If more output poweris desired Control Circuit 135 may use Digital Input Circuit 105 selectthe same set of Discharge Switches 130A in each bank. Alternatively, ifa larger dynamic range is desired, Digital Input Circuit 105 may be usedto select different sets of Discharge Switches 130 in each bank.

In the serial mode, Control Circuit 135 is configured to alternativelyperform Conversion Periods 210 on First Bank 510 and Second Bank 515.For example, Recharge Switches 125 and Discharge Switches 130 may be setfor a Conversion Period in First Bank 510 while the correspondingswitches in Second Bank 515 are set for a Recharge Period 220, andvice-versa. The serial use of two banks allows for a doubling of theconversion frequency.

FIGS. 6A-6C illustrate output waveforms generated using First Bank 510and Second Bank 515 used in a serial operation, according to variousembodiments of the invention. The output of each of First Bank 510 andSecond Bank 515 comprises a series of pulses as further discussedelsewhere herein, e.g., with regard to FIGS. 2A and 2B. FIGS. 6A and 6Billustrate an example of how the Conversion Period 210 and RechargePeriod 220 of First Bank 510 may be offset in time relative to theConversion Period 210 and Recharge Period 220 of Second Bank 515. TheConversion Period 210 of First Bank 510 may overlap with the RechargePeriod 220 of Second Bank 515. Likewise, the Conversion Period 210 ofSecond Bank 515 may overlap with the Recharge Period 220 of First Bank510. FIG. 6C illustrates the sum of the output of First Bank 510 andSecond Bank 515 as would be found at Output Circuit 110. The frequencyof this summed output is greater than that produced by either of theindividual banks. In alternative embodiments, three, four or more banksare used to achieve an even greater frequency.

Unit Cells 115 may be arranged in a binary bank or a thermometer bank. Athermometer bank is a bank in which each Unit Cell 115 provides the sameoutput power when activated. For example, a thermometer bank includingfour Unit Cells 115 (each able to provide one unit of output) canrepresent five different output levels 0, 1, 2, 3, and 4. Two of UnitCells 115 are activated to produce an output level of 2 and all for UnitCells 115 are activated to produce an output level of 4. Three unitcells in a thermometer bank are sufficient to convert two bits of binarydata to an analog signal. In various embodiments, a thermometer bank mayinclude 2, 3, 4, 5, 6, 7, 8 or more Unit Cells 115.

A binary bank is a bank in which different Unit Cells 115 are configuredto provide different output power when activated. For example, in atypical binary bank a first Unit Cell 115 may is configured to provideone unit of output power, a second Unit Cell 115 is configured toprovide two units of output power and a third Unit Cell 115 isconfigured to provide four units of output power. If the first and thirdUnit Cells 115 are activated then a total of five units of output powerare provided Likewise, if all three Unit Cells 115 are activated then atotal of 7 units of output power are provided. Each Unit Cell 115 in abinary bank is sufficient to convert one bit of digital data. Forexample, a binary bank including four Unit Cells 115 can convert fourbinary bits to an analog signal. In various embodiments, a binary bankmay include 2, 3, 4, 5, 6, 7, 8 or more Unit Cells 115.

FIG. 7 illustrates various embodiments of Digital-to-Analog Circuit 100wherein First Bank 510 comprises a Thermometer Bank 710 and Second Bank515 comprises a Binary Bank 715. In these embodiments ofDigital-to-Analog Circuit 100, Digital Input Circuit 105 includes a DataLatch 720, an Encoder 725, and a Delay 730. Data Latch 720, Encoder 725and Delay 730 may be considered components of Digital Input Circuit 105.In these embodiments Data Latch 720 is configured to receive five bitsof digital binary data to be converted to an analog signal. Data Latch720 provides two of these bits to Thermometer Bank 710 and three ofthese bits to Binary Bank 715. In alternative embodiments of theinvention Data Latch 720 is configured to receive a different number ofbits and/or divide the bits differently between two or more banks.

The Unit Cells 115 within Binary Bank 715 are configured to provide oneunit (1×), two units (2×) or four units (4×) of output power. Incontrast, the Unit Cells 115 within Thermometer Bank 710 are eachconfigured to provide eight units (8×) of output power. When used inparallel, in the illustrated embodiments, Binary Bank 715 is configuredto convert the least significant bits of the digital data andThermometer Bank 710 is configured to convert the most significant bits.Output Circuit 110 includes two resistors to ground and is configured toreceive the combined outputs of Binary Bank 715 and Thermometer Bank710. The resistors are configured to convert the combined outputs to avoltage. The Unit Cells 115 within Binary Bank 715 may be configured toprovide different amounts of power output through the use of differentcharging voltages, the use of different capacitor values, and/or thelike.

Data Latch 720 is configured to store the received digital data andstore it until digital data can be converted to the analog signalaccording to the timing of Control Circuit 135.

Encoder 725 is configured to encode bits received from Data Latch 720for use by the Unit Cells 115 within Thermometer Bank 710. For example,if the received bits represent a binary value of two then the output ofEncoder 725 is encoded to turn on two of the Discharge Switches 130Likewise, if the received bits represent a binary value of four then theoutput of Encoder 725 is encoded to turn on four of the DischargeSwitches 130 in Thermometer Bank 710.

Delay 730 is configured to delay digital signals received from DataLatch 720 to compensate for any delay that occurs in Encoder 725. Delay730 is configured to delay the signals such that the data is received bythe Unit Cells 155, within Binary Bank 715 and Thermometer Bank 710, atapproximately the same time.

FIG. 8 illustrates a Transmitter System 800 including Digital-to-AnalogCircuit 100, according to various embodiments of the invention.Digital-to-Analog Circuit 100 replaces a digital-to-analog converter, afilter and mixer typically found in transmitter systems of the priorart. Transmitter System 800 includes a Data Latch 810 configured toreceive and hold digital data. Data Latch 810 is optionally configuredto received both “I” and “Q” data from a digital signal processor. DataLatch 810 optionally includes parts of Digital Input Circuit 105.Digital input data is communicated from Data Latch 810 toDigital-to-Analog Circuit 100 for conversion to an analog output circuitas discussed elsewhere herein. The output of Digital-to-Analog Circuit100 is an analog representation of the digital input data and is alsomixed with the sampling frequency of Digital-to-Analog Circuit 100.Because the operation of Digital-to-Analog Circuit 100 achieves bothdigital-to-analog conversion and mixing at the same time, an additionalmixer is not required.

The analog output of Digital-to-Analog Circuit 100 is provided to a bandselection Filter 820. Filter 820 is a configured to remove a basebandsignal and/or any unwanted RF sidebands. Filter 820 is typicallydisposed before an Amplifier 830, although in some embodiments mayfollow Amplifier 830. Amplifier 830 is configured to boost the signal toa required level for transmission. The output of Amplifier 830 isreceived by a Coupler 840. Coupler 840 is configured to provide theproper impedance for transmission and optionally provides diplexerfunctionality. Coupler 840 may include a transformer, antenna, currentcopier, a balun, or the like. Filter 820, Amplifier 830 and/or Coupler840 are optionally part of Output Circuit 110.

FIG. 9 illustrates a method of converting a digital input signal to ananalog output signal, according to various embodiments of the invention.This method may be performed using digital-to-Analog Circuit 100. Themethod includes charging a plurality of capacitors and then dischargingselected members of the plurality of capacitors based on a digitalinput. The plurality of capacitors are optionally charged before thedigital input is received. The discharge of the selected membersconstitute the analog output signal, which may be expressed as acurrent, power or voltage, etc.

More specifically the method illustrated in FIG. 9 includes a ChargingStep 910 in which both a first capacitor and a second capacitor, e.g.,Capacitors 120A and 120B, are charged using one or more voltage sourcessuch as Voltage Source 140. These capacitors are typically charged atthe essentially the same time in parallel operation. In serial operationthese capacitors are charged at the same time when in the same bank andoptionally at different times when in different banks. Charging Step 910optionally includes charging three, four or more of Capacitors 120.

In an Operate Switch Step 920, a first of Recharge Switches 125 isopened such that the first capacitor is electrically disconnected fromthe voltage source. In an Operate Switch Step 930 a second of RechargeSwitches 125 is opened such that the second capacitor is electricallydisconnected from the voltage source. In parallel operation, OperateSwitch Step 920 and Operate Switch Step 930 are performed atapproximately the same time. In serial operation Operate Switch Step 920and Operate Switch Step 930 are optionally performed at different timeswhen the switches control charging of capacitors in different banks, andtypically performed at approximately the same time when the switchescontrol charging of capacitors in the same bank.

In a Receive Signal Step 940 a digital signal is received by DigitalInput Circuit 105. This digital signal includes at least two bits and isthe signal to be converted to an analog signal. Receive Signal Step 940optionally includes dividing bits of the digital signal between FirstBank 510 and Second Bank 515. Further, Receive Signal Step 940optionally includes encoding the binary data using Encoder 725.

In a Set Switch Step 950 a first discharge switch, e.g., DischargeSwitch 130A, is closed responsive to the value of the digital signalreceived by Digital Input Circuit 105 in Receive Signal Step 940.Closure of the first discharge switch allows the discharge of thecorresponding capacitor. For example, closing Discharge Switch 130Aresults in the discharge of Capacitor 120A to Output Circuit 110.

In a Set Switch Step 960 a second discharge switch, e.g., DischargeSwitch 130B, is closed responsive to the value of the digital signalreceived by Digital Input Circuit 105 in Receive Signal Step 940.Closure of the second discharge switch allows the discharge of thecorresponding capacitor. For example, closing Discharge Switch 130Bresults in the discharge of Capacitor 120B to Output Circuit 110. Inparallel operation, Set Switch Step 950 and Set Switch Step 960 areperformed at approximately the same time. In serial operation Set SwitchStep 950 and Set Switch Step 960 are optionally performed at differenttimes when the switches control discharging of capacitors in differentbanks, and typically performed at approximately the same time when theswitches control discharging of capacitors in the same bank. Dischargingof the first capacitor can be performed independently of discharging ofthe second capacitor, depending on the value of the digital signal.

In a Provide Output Step 970 the discharge of the first and secondcapacitors are provided to Output Circuit 110 through the first andsecond discharge switches. The charge discharged from the first andsecond capacitors, and optionally further capacitors depending on thevalue of the digital signal, represents the output of the method atOutput Circuit 110. The power, e.g., charge and current, of the outputis responsive to the settings of the first discharge switch and thesecond discharge switch.

In alternative embodiments one, three, four or more capacitors aredischarged responsive to the value of the digital signal. The frequencyof the output at output Circuit 110 is optionally greater than afrequency at which digital input data is received by Digital InputCircuit.

FIG. 10 illustrates alternative embodiments of Digital-to-Analog Circuit100 in which capacitors are charged based on a digital input. Theembodiments illustrated in FIG. 10 differ from those illustrated by FIG.1 in that the digital information is used to control charging ratherthan discharging of the Capacitors 120. Specifically, Digital InputCircuit 105 is coupled to Recharging Capacitors 125 and controls whichmembers of Capacitors 120 are charged during Recharge Period 220. Only asubset of Capacitors 120 may be charged during Recharge Period 220depending on the digital input value received by Digital Input Circuit105. During Conversion Period 210 all of Discharge Switches 130 aretypically closed to allow charge from those members of Capacitors 120that were charged during Recharge Period 220 to discharge into OutputCircuit 110. The analog output of Digital-to-Analog Circuit 100 consistsof the charge discharged from Capacitors 120 during Conversion Period210. In alternative embodiments, Digital Input Circuit 105 is configuredto selectively close a subset of Recharge Switches 125 during RechargePeriod 220 and also to selectively close a subset of Discharge Switches130 during Conversion Period 210.

FIG. 11A-11C illustrate alternative embodiments of Output Circuits 110,according to various embodiments of the invention. These embodimentsallow charge discharged from Capacitors 120 to be temporally stored inone or more Storage Capacitor 1120 prior to being provided as an analogcharge output of Digital-to-Analog Converter 100. The use of StorageCapacitor 1120 is optionally used to make the RC time constant of theoutput independent of the digital value being converted. For example, inthe embodiments of Digital-to-Analog Circuit 100 illustrated by FIG. 1the capacitance and, thus, the RC time constant of the output will bedependent on the sum of the capacitance of the capacitors providing thecharge. The number and identities of these capacitors will varydepending on the value of the digital input. By transferring the chargeto one or more Storage Capacitor 1120 and then providing the analogoutput the capacitance of the output is that of the one or more StorageCapacitor 1120. This capacitance, and the resulting RC time constant, isindependent of the digital value being converted. The charge may then bedelivered to additional circuits such as Filter 820, Amplifier 830,Coupler 840, any combination thereof, or the like. In some embodiments,each of Capacitor 120 are charged to the same voltage and thenselectively discharged to Storage Capacitor 1120. Alternatively, each ofCapacitor 120 is charged to one of two alternative levels as a functionof a digital input and then discharged to Storage Capacitor 1120.Alternatively, each of Capacitor 120 is charged to three or morealternative voltages as a function of a digital input and thendischarged to Storage Capacitor 1120. The digital input is optionallyused to select states of both Recharge Switches 125 and DischargeSwitches 130. The use of both sets of switches is optionally used toperform logic operations.

FIG. 11A illustrates embodiments of Output Circuit 110 including anOutput Switch 1110 and a Storage Capacitor 1120. Storage Capacitor 1120is configured to receive the output charge from Capacitors 120 viaDischarge Switches 130 while Output Switch 1110 is open. After theoutput charge is received by Storage Capacitor 1120, Discharge Switches130 are opened and Output Switch 1110 is closed. The output charge isthen delivered from Storage Capacitor 1120. This provides the analogcharge output a consistent RC time constant dependant on the capacitanceof Storage Capacitor 1120 and the impedance of Output Switch 1110.

FIG. 11B illustrates differential embodiments of Output Circuit 110including several Storage Capacitor 1120, individually labeled1120A-1120D. Each of Storage Capacitor 1120 typically have the samecapacitance. The embodiments illustrated in FIG. 11B are configured toreceive charge from a differential embodiment of Digital-to-AnalogCircuit 100, e.g., embodiments including the differential Unit Cells 115illustrated in FIGS. 3A-3D. The differential charge signal is receivedin alternative phases at Inputs 1140A and 1140B. In a first phase OutputSwitches 1130C and 1130D are closed while Output Switches 1130A and1130B are open, and the differential charge output is provided toStorage Capacitors 1120C and 1120D. In a second phase Output Switches1130A and 1130B are closed while Output Switches 1130C and 1130D areopen, and the differential charge output is provided to StorageCapacitors 1120A and 1120B. In the first phase part of the differentialanalog charge output is provided at Differential Output 310 from StorageCapacitors 1120A and 1120B by closing Output Switches 1110A and 1110B.Likewise, in the second phase the other part of the differential analogcharge output is provided at Differential Output 310 by closing OutputSwitches 1110C and 1110D. In typically operation, Storage Capacitors1120A and 1120B receive charge from Unit Cells 115 while StorageCapacitors 1120C and 1120D are providing stored charge as an output, andvice versa.

FIG. 11C illustrates embodiments of Output Circuit 110 with an OutputSwitch 1110 but without a Storage Capacitor 1120. Storage Capacitor 1120can be omitted in embodiments of Digital-to-Analog Circuit 100 in whichthe same Discharge Switches 130 are closed during Conversion Period 210independent of the digital value being converted. For example, in thoseembodiments illustrated by FIG. 10. The functionality of StorageCapacitor 1120 can be achieved by redistributing charge among Capacitors120C prior to providing the charge as an analog output. Specifically, ifDischarge Switches 130 (FIG. 10) are closed while Output Switch 1110 isopen charge will flow from those members of Capacitors 120 that werecharged responsive to the digital input to the other members ofCapacitors 120. The charge is then stored on the entire set ofCapacitors 120 until Output Switch 1110 is closed. When Output Switch1110 is closed the RC time constant of the analog charge output isdependent on the capacitance of the entire set of Capacitors 120 and theoutput impedance of the various switches.

The embodiments of Unit Cell 115 illustrated in FIGS. 3A-3D areoptionally adapted for use as alternative embodiments of Output Circuit110. For example, the Capacitors 120 and Discharge Switches 130illustrated in FIGS. 3A and 3B may be used as Storage Capacitors 1120and Output Switches 1110 in alternative embodiments of Output Circuit110.

FIGS. 12A-12C include a timing diagram of a digital-to-analog circuitincluding a summing capacitor. FIG. 12A shows charge at one ofCapacitors 120, e.g. Capacitor 120A. As discussed with respect to FIG.2B, Capacitor 120A is charged during Recharge Period 220 and selectivelydischarged during Conversion Period 210. In embodiments, such as thoseillustrated by FIG. 1, the discharging of Capacitor 120A is dependent onthe digital input value. In embodiments, such as those illustrated byFIG. 10, the charging of Capacitor 120A is dependent on the digitalinput value. FIG. 12B illustrates how the charge discharged fromCapacitor 120A, and optionally other members of Capacitors 120, isreceived by Storage Capacitor 1120. Storage Capacitor 1120 is chargedduring Conversion Period 210 and discharged during Recharge Period 220.As shown in FIG. 12C this discharge from Storage Capacitor 1120 occursduring Recharge Period 220 while Capacitors 120 are being charged.

FIG. 13 illustrates methods of converting a digital input signal to ananalog output signal, according to various embodiments of the invention.In these methods Capacitors 120 are selectively charged and dischargedresponsive to a digital input value. The charge discharged fromCapacitors 120 is stored in Storage Capacitor 1120 before being providedas an analog charge output.

In Charging Step 910 Capacitors 120 are charged as discussed elsewhereherein. In a Set Switches Step 1320, Recharge Switches 125 are opened soas to decouple Capacitors 120 from Voltage Source 140. Set Switches Step1320 may include, for example, Operate Switch Step 920 and OperateSwitch Step 930. In Receive Signal Step 940 a signal representing adigital value to be converted to an analog signal is received, asdiscussed elsewhere herein. Receive Signal Step 940 may occur prior toCharging Step 910 and/or Set Switches Step 1320.

In a Set Switches Step 1350 one or more Discharge Switches 130 areclosed so as to discharge Capacitors 120. Set Switches Step 1350 mayinclude, for example, Set Switch Step 950 and Set Switch Step 960. Theswitches closed in Set Switches Step 1350 are optionally selected basedon the digital input value received in Receive Signal Step 940.

In a Store Charge Step 1360 the charge discharged from Capacitors 120 inSet Switches Step 1350 is stored in Storage Capacitor 1120. As isdiscussed elsewhere herein, in some embodiments Digital-to-AnalogCircuit 100 is configured such that Capacitors 120 function as StorageCapacitor 1120. In these embodiments, charge is redistributed amongCapacitors 120, e.g., flows between members of Capacitors 120, as aresult of Set Switches Step 1350.

In a Set Switches Step 1365 one or more Output Switches 1110 are closedsuch that the charge stored in Storage Capacitor 1120 can be provided asan analog charge output. This output is optionally differential and isprovided in Provide Output Step 970.

The output of Digital-to-Analog Circuit 100 includes a mixture of thefrequency content of the digital input signal and a frequency at whichsampling occurs. This mixture typically includes two images of thedigital input signals as sidebands to the sampling frequency.Digital-to-Analog Circuit 100 is configured to perform both adigital-to-analog conversion and frequency mixing through the sameoperations. I/Q (in phase plus quadrature phase) modulation isoptionally used to suppress one of the two sidebands and provide fullpower to the other sideband.

FIG. 14 illustrates an I/Q Modulation System 1400 in configured tosuppress one of two sidebands. I/Q Modulation System 1400 includes a “Q”Input Path 1410 and an “I” Input Path 1415. These input paths areconfigured to receive a baseband signal. This baseband signal caninclude a plurality of signals over a range of frequencies. Input Path1410 is coupled to a Phase Shifter 1420A configured to apply a 90 degreephase shift to the input signal to produce the “Q” version of thesignal. Input Path 1415 is coupled to a Mixer 1425A configured to mix ormultiplex two signals. The other input to Mixer 1425A is received from aCarrier Source 1430. Carrier Source 1430 is configured to provide asinusoidal wave at a carrier frequency. This sinusoidal wave is alsoprovided to a second Phase Shifter 1420B, also configured to apply a 90degree phase shift. The outputs of Phase Shifter 1420A and Phase Shifter1420B are mixed in a second Mixer 1425B. The outputs of Mixer 1425A andMixer 1425B are added in a Summer 1435. This results in a final Output1440 in which the baseband signal is moved to a higher frequency as asideband of the carrier frequency. In the prior art sideband suppressionsystems such as I/Q Modulation System 1400 are typically implemented inthe digital domain.

FIGS. 15A and 15B illustrate two alternative circuits in whichDigital-to-Analog Circuit 100 is used to both perform adigital-to-analog conversion and also achieve sideband suppression.These circuits produce essentially a single sideband of a carrierfrequency from a baseband signal. The carrier frequency is the frequencyat which digital-to-analog conversion takes place.

In the circuit of FIG. 15A two Analog-to-Digital Converters,individually labeled 100A and 100B are disposed to receive the “I” and“Q” output of a Data Latch 1510. The “Q” data signal is a phase shiftedversion of the “I” data signal. The phase shift applied to the “Q” datais:

$Q_{Phase} = {2\; {\pi \left\lbrack {\frac{1}{4} + \frac{f_{b}}{4f_{c}}} \right\rbrack}}$

Where f_(b) is the frequency of the based band signal and f_(c) is thefrequency of the output of Clock 1520 and Q_(phase) is in radians. Eachof Analog-to-Digital Converters 100A and 100B receive a clock signalfrom a Clock 1520. This clock signal is used to determine the samplingrate and timing of the digital-to-analog conversion. The clock signalreceived by Digital-to-Analog Converter 100B is shifted 90 degrees usinga Phase Shifter 1530. Digital-to-Analog Converter 110 A and 100B areoptionally configured to produce analog output representative of thedigital input for a first half of the clock cycle and to produce ananalog output representing a binary negated value of the digital inputfor a second half of the clock cycle. Analog-to-Digital Converters 100Aand 100B are each configured to generate a differential output which canbe sampled across Loads 1540A and 1540B. Loads 1540A and 1540B areconfigured to combine the first and second analog outputs so as toproduce a single sideband output, e.g., an output in which a secondsideband is at least partially suppressed.

In the circuit of FIG. 15B the “I” and “Q” signals are combined in aMultiplexer 1550 and then provided to a Binary Negator 1560. Multiplexer1550 switches between the “I” and “Q” data inputs half clock cycle.Binary Negator 1560 is configured to negate the multiplexer output onevery other clock cycle, e.g. on every odd clock cycle. The output ofBinary Negator 1560 is provided to Digital-to-Analog Converter 100. Adifferential output of Analog-to-Digital Converters 100 is provided toLoads 1540A and 1540B. A PLL 1570 (phase-locked loop) is used togenerate two clocks of f and f/2 from a clock 1520. Multiplexer 1550 andAnalog-to-Digital Converters 100 receive the output at f while BinaryNegator 1560 receives the output at f/2. These outputs are themodulation of the Q and I data modulated by a sine and cosine of thefrequency f/2, respectively, The output of Analog-to-Digital Converters100 is a sideband suppressed signal modulated at half the clockfrequency received by Analog-to-Digital Converters 100.

FIG. 16 illustrates alternative embodiments of Unit Cell 115, accordingto various embodiments of the invention. These embodiments includeCharging Switch 125A and Charging Switch 125B. Charging Switch 125A andCharging Switch 125B are optionally n-type field effect transistors, thebase of Charging Switch 125A being electrically connected to the gate ofCharging Switch 125B, and the base of Charging Switch 125B beingelectrically connected to the gate of Charging Switch 125A. ChargingSwitch 125A and Charging Switch 125B allow the charging of Capacitors120A and 120B in alternative clock cycles. The other sides of Capacitors120A and 120B are electrically connected to an output of Clock 1520. AnInverter 1610 is configured such that Capacitors 120A and 120B receivelogically opposite clock signals.

When Capacitor 120A receives a high clock signal a Node 1613 is raisedto twice the output of Voltage Source 140 (2×V_(dd)) and a Node 1615 islowered in potential by V_(dd) (as a result of the other side ofCapacitor 120B being lowered in potential from V_(dd) to 0 by the clocksignal). Raising Node 1613 closes Charging Switch 125B and allowsCapacitor 120B to be charged to V_(dd) at Node 1615. On the low clocksignal Node 1615 is raised to 2×V_(dd) and Node 1613 is lowered inpotential by V_(dd). This closes Charging Switch 125A and allowsCapacitor 120A to be charged to V_(dd) at Node 1613. As a result thevoltages at Nodes 1613 and 1615 alternate between V_(dd) and 2 timesV_(dd) at the frequency of Clock 1520.

A P-Enable Input 1620 and an N-Enable Input 1630 are alternatively usedto direct the discharge from Capacitors 120A and 120B to a P-Output 1640and an N-Output 1650, respectively. The P-Enable Input 1620 iselectrically coupled to Discharge Switch 130C and N-Enable Input 1630 iselectrically coupled to Discharge Switch 130D. In some embodimentsDischarge Switches 130C and 130D are n-type field effect transistors,and P-Enable Input 1620 and an N-Enable Input 1630 are coupled to thegates thereof. A Switch 1640 and a Switch 1650 are configured to assurethat the voltage at Nodes 1613 and 1615 does not fall below V_(dd). Forexample, Switches 1640 and 1650 may be p-type field effect transistorsthe base of each being electrically coupled to the gate of the other,respectively.

As discussed elsewhere herein, switches such as Recharge Switches 125and Discharge Switches 130 may include field effect transistors (FETs).The ON resistance of a field effect transistor is dependent on its gateto source voltage. The ON resistance is inversely proportional to thegate-source voltage. Therefore when used in circumstances where thesource voltage varies, such as Discharge Switches 130 or RechargeSwitches 125 of the various Unit Cell 115 disclosed herein. In theseapplications the gate-source voltage, and thus the on resistance, canchange over time. This reduces the efficiency of the circuit.

In order to overcome this problem, the switches discussed herein areoptionally bootstrapped to achieve an ON resistance that is essentiallyindependent of source voltage. FIG. 17 illustrates an example of abootstrapped switch as may be included in various embodiments of theinvention.

The resistance between a source (s) and drain (d) of a FET 1705 is keptconstant in the ON state by keeping the gate-source voltage a constantvalue of V_(dd)−V_(ss). In the OFF state of FET 1705, Switches 1710,1715 and 1720 are closed while Switches 1725 and 1730 are open. Thisswitch setting will turn FET 1705 off assuming that V_(in, A) does notdrop below V_(SS). This switch setting will also charge Capacitor 1735to V_(dd)−V_(ss). In the ON state of FET 1705, Switches 1725 and 1730are closed while Switches 1710, 1715 and 1720 are open. This switchsetting applies the charge on Capacitor 1735 between the gate and sourceof FET 1705. Specifically, the gate-source voltage will be V_(dd)−V_(ss)and the gate voltage will be (V_(dd)−V_(ss))+V_(in,A). The gate-sourcevoltage is independent of the source voltage and the resistance throughFET 1705 will be approximately constant in the ON state as the sourcevoltage varies. Switches 1710, 1715, 1720, 1725 and 1730 optionallyinclude transistors.

Several embodiments are specifically illustrated and/or describedherein. However, it will be appreciated that modifications andvariations are covered by the above teachings and within the scope ofthe appended claims without departing from the spirit and intended scopethereof. For example the digital-to-analog circuit described herein maybe used on systems and applications other than the transmitter system ofFIG. 8. The circuits described herein are optionally implemented in CMOSintegrated circuits. The voltage sources discussed are meant to includecurrent sources or combinations of voltages sources and current sources,in addition to devices that one of ordinary skill in the art wouldconsider voltage sources.

In some embodiments of the invention, Control Circuit 135 is configuredto close Recharge Switches 125 during Recharge Period 220 and to closeDischarge Switches 130 during Conversion Period 210, independent of adigital value to be converted. In these embodiments an additional set ofdischarge switches (not shown) is configured to selectively discharge asubset of Capacitors 120, e.g., to ground, after Recharge Period 220 andbefore Conversion Period 210. This subset is selected responsive to thedigital input value using Digital Input Circuit 105. During ConversionPeriod 210 those Capacitors 120 that were not previously discharged,i.e., not members of the selected subset, provide charge throughDischarge Switches 130 to Output Circuit 110. The Output Circuit 110illustrated by FIG. 11C is optionally used with these embodiments.

The embodiments discussed herein are illustrative of the presentinvention. As these embodiments of the present invention are describedwith reference to illustrations, various modifications or adaptations ofthe methods and or specific structures described may become apparent tothose skilled in the art. All such modifications, adaptations, orvariations that rely upon the teachings of the present invention, andthrough which these teachings have advanced the art, are considered tobe within the spirit and scope of the present invention. Hence, thesedescriptions and drawings should not be considered in a limiting sense,as it is understood that the present invention is in no way limited toonly the embodiments illustrated.

1. A method of converting a digital input signal to an analog outputsignal, the method comprising: receiving the digital input signalincluding at least two bits; charging both a first capacitor and asecond capacitor at the same time using one or more voltage sources;opening a first recharge switch to electrically disconnect the firstcapacitor from the one or more voltage sources; opening a secondrecharge switch to electrically disconnect the second capacitor from theone or more voltage sources; setting a first discharge switch configuredto control discharge of the first capacitor; setting a second dischargeswitch configured to control discharge of the second capacitor, whereincharging of the first and second capacitor or setting of the first andsecond discharge switches is responsive to the two bits; and providing acharge pulse through the first discharge switch and the second dischargeswitch, the analog output signal being differential and including chargedischarged from the first capacitor and the second capacitor.
 2. Themethod of claim 1, wherein the analog output signal includes a mix ofthe digital input signal and a sampling frequency of thedigital-to-analog conversion.
 3. The method of claim 2, wherein thesampling frequency is greater than 1 GHz.
 4. The method of claim 2,wherein the analog output signal is within a side band of a mixture ofthe digital input signal and the sampling frequency.
 5. The method ofclaim 1, further comprising passing the analog output signal through afilter.
 6. The method of claim 1, further comprising amplifying theanalog output signal and communicating the amplified output signalthrough a communication medium.
 7. The method of claim 1, furthercomprising storing the charge provided through the first dischargeswitch and the second discharge switch in at least one storage capacitorprior to including the charge in the analog output signal.
 8. The methodof claim 1, wherein the analog output signal is between approximately1.5 GHz and 2 GHz.
 9. The method of claim 1, wherein the analog outputsignal is between 2 GHz and 3.2 GHz.
 10. The method of claim 1, whereinthe analog output signal includes a frequency band at least 50 MHz inwidth.
 11. A digital-to-analog conversion circuit, comprising: a digitalinput circuit for receiving a digital input signal including at leasttwo bits; a first capacitor and a second capacitor coupled in parallel;a first recharge switch coupled between one or more voltage sources andthe first capacitor; a second recharge switch coupled between the one ormore voltage sources and the second capacitor; a first discharge switchcoupled between the first capacitor and an output; a second dischargeswitch coupled between the second capacitor and the output; and acontrol circuit coupled to the digital input circuit, the first rechargeswitch and the second recharge switch, the control circuit operable to:close the first recharge switch and the second recharge switch to chargethe first capacitor and the second capacitor at the same time during arecharge period; open the first recharge switch and the second rechargeswitch to electrically disconnect the first capacitor and the secondcapacitor from the one or more voltage sources during a conversionperiod; and selectively close the first discharge switch and the seconddischarge switch during the conversion period to control discharge ofthe first capacitor and the second capacitor to produce an analog outputsignal, the analog output signal being differential and including chargedischarged from the first capacitor and the second capacitor; whereincharging or discharging of the first capacitor and the second capacitorby the control circuit is responsive to the two bits.
 12. Thedigital-to-analog conversion circuit of claim 11, wherein the analogoutput signal includes a mix of the digital input signal and a samplingfrequency of the digital-to-analog conversion circuit.
 13. Thedigital-to-analog conversion circuit of claim 12, wherein the samplingfrequency is greater than 1 GHz.
 14. The digital-to-analog conversioncircuit of claim 12, wherein the analog output signal is within a sideband of a mixture of the digital input signal and the samplingfrequency.
 15. The digital-to-analog conversion circuit of claim 11,further comprising: at least one storage capacitor for storing thecharge provided through the first discharge switch and the seconddischarge switch prior to including the charge in the analog outputsignal.
 16. The digital-to-analog conversion circuit of claim 11,wherein the analog output signal includes a frequency band at least 50MHz in width.
 17. A sideband suppression system comprising: a clockconfigured to provide a clock signal; an I/Q data latch configured toreceive digital input data and provide an “I” signal and a “Q” signalrepresentative of the digital input data; a phase shifter configured toproduce a phase shifted copy of the clock signal; a first differentialdigital-to-analog converter configured to receive the “I” signal and theclock signal, and to produce a first analog output including twosidebands of the “I” signal around a sampling frequency of the firstdigital-to-analog converter; a second differential digital-to-analogconverter configured to receive the “Q” signal and the phase shiftedcopy of the clock signal, and to produce a second analog outputincluding two sidebands of the “Q” signal around a sampling frequency ofthe second digital-to-analog converter; and a load circuit configured tocombine the first and second analog outputs so as to produce a singlesideband output.
 18. The system of claim 17, wherein the single sidebandoutput includes charge pulses representative of the digital input data.19. A sideband suppression system comprising: a clock configured toprovide a clock signal; an I/Q data latch configured to receive digitalinput data and provide an “I” signal and a “Q” signal; a multiplexerconfigured to multiplex the “I” and “Q” signals; a binary negatorconfigured to negate an output of the multiplexer output on every othercycle of the clock signal; a differential digital-to-analog converterconfigured to receive an output of the binary negator and produce ananalog charge pulse output representative of the digital input data, theanalog charge pulse output including a single sideband of the clocksignal, a second sideband being suppressed; and a load circuitconfigured to receive the analog charge pulse output.
 20. The sidebandsuppression system of claim 19, wherein the analog charge pulse outputis differential.